NTB60N06L ,Power MOSFET 60 Amps, 60 Volts, Logic Level3R DRAIN-TO-SOURCE RESISTANCE (NORMALIZED) R , DRAIN-TO-SOURCE RESISTANCE () I , DRAIN CURRENT (AM ..
NTB60N06T4G ,Power MOSFET 60 Amps, 60 VoltsMAXIMUM RATINGS (T = 25°C unless otherwise noted)JMARKINGRating Symbol Value UnitDIAGRAMS4Drain−to− ..
NTB6410AN ,NTB6410ANELECTRICAL CHARACTERISTICS (T = 25°C Unless otherwise specified) JCharacteristics Symbol Test Condi ..
NTB6410ANG , N-Channel Power MOSFET 100 V, 76 A, 13 mΩ
NTB6410ANT4G , N-Channel Power MOSFET 100 V, 76 A, 13 mΩ
NTB6411AN ,NTB6411ANELECTRICAL CHARACTERISTICS (T = 25°C Unless otherwise specified) JCharacteristics Symbol Test Condi ..
OPA847ID ,Wideband, Ultra-Low Noise,Voltage Feedback Operational Amplifier with ShutdownHarmonic Distortion (dBc)(1)ABSOLUTE
OPA847IDBVR ,Wideband, Ultra-Low Noise,Voltage Feedback Operational Amplifier with ShutdownOPA847OPA847
OPA847IDBVT ,Wideband, Ultra-Low Noise,Voltage Feedback Operational Amplifier with ShutdownTYPICAL CHARACTERISTICS: V = ±5VST = 25°C, G = +20V/V, R = 39.2Ω , and R = 100Ω , unless otherwise ..
OPA847IDBVTG4 ,Wideband, Ultra-Low Noise,Voltage Feedback Operational Amplifier with Shutdown 6-SOT-23 -40 to 85 SBOS251E – JULY 2002 – REVISED DECEMBER 2008Wideband, Ultra-Low Noise, Voltage-FeedbackOPERATIONAL ..
OPA860 ,Wide Bandwidth OPERATIONAL TRANSCONDUCTANCE AMPLIFIER (OTA) and BUFFERMAXIMUM RATINGSPower Supply ±6.5VDCInternal Power Dissipation See Thermal InformationDifferential I ..
OPA860ID ,Wide Bandwidth OPERATIONAL TRANSCONDUCTANCE AMPLIFIER (OTA) and BUFFERFEATUREScentered about zero. The transconductance of the• Low Quiescent Current (11.2mA)OTA can be ..
NTB60N06L
Power MOSFET 60 Amps, 60 Volts, Logic Level
3R DRAIN-TO-SOURCE RESISTANCE (NORMALIZED) R , DRAIN-TO-SOURCE RESISTANCE () I , DRAIN CURRENT (AMPS)DS(on), DS(on) DR , DRAIN-TO-SOURCE RESISTANCE ()DS(on)I , LEAKAGE (nA) I , DRAIN CURRENT (AMPS)DDSSNTP60N06L, NTB60N06LPOWER MOSFET SWITCHINGSwitching behavior is most easily modeled and predicted The capacitance (C ) is read from the capacitance curve atissby recognizing that the power MOSFET is charge a voltage corresponding to the off-state condition whencontrolled. The lengths of various switching intervals (Δt) calculating t and is read at a voltage corresponding to thed(on)are determined by how fast the FET input capacitance can on-state when calculating t .d(off)be charged by current from the generator. At high switching speeds, parasitic circuit elementscomplicate the analysis. The inductance of the MOSFETThe published capacitance data is difficult to use forsource lead, inside the package and in the circuit wiringcalculating rise and fall because drain-gate capacitancewhich is common to both the drain and gate current paths,varies greatly with applied voltage. Accordingly, gateproduces a voltage at the source which reduces the gate drivecharge data is used. In most cases, a satisfactory estimate ofcurrent. The voltage is determined by Ldi/dt, but since di/dtaverage input current (I ) can be made from aG(AV)is a function of drain current, the mathematical solution isrudimentary analysis of the drive circuit so thatcomplex. The MOSFET output capacitance alsot = Q/IG(AV)complicates the mathematics. And finally, MOSFETs havefinite internal gate resistance which effectively adds to theDuring the rise and fall time interval when switching aresistance of the driving source, but the internal resistanceresistive load, V remains virtually constant at a levelGSknown as the plateau voltage, V . Therefore, rise and fall is difficult to measure and, consequently, is not specified.SGPtimes may be approximated by the following: The resistive switching time variation versus gateresistance (Figure 9) shows how typical switchingt = Q x R /(V - V )r 2 G GG GSPperformance is affected by the parasitic circuit elements. Ift = Q x R /Vf 2 G GSPthe parasitics were not present, the slope of the curves wouldmaintain a value of unity regardless of the switching speed.whereThe circuit used to obtain the data is constructed to minimizeV = the gate drive voltage, which varies from zero to VGG GGcommon inductance in the drain and gate circuit loops andR = the gate drive resistanceGis believed readily achievable with board mountedand Q and V are read from the gate charge curve.2 GSP components. Most power electronic loads are inductive; thedata in the figure is taken with a resistive load, whichDuring the turn-on and turn-off delay times, gate current isapproximates an optimally snubbed inductive load. Powernot constant. The simplest calculation uses appropriateMOSFETs may be safely operated into an inductive load;values from the capacitance curves in a standard equation forhowever, snubbing reduces switching losses.voltage change in an RC network. The equations are:t = R C In [V /(V - V )]d(on) G iss GG GG GSPt = R C In (V /V )d(off) G iss GG GSP8000V = 0 V V = 0 VDS GST = 25°CJ6000Ciss4000CrssCiss2000CossCrss010 5 0 5 10 15 20 25V VGS DSGATE-TO-SOURCE OR DRAIN-TO-SOURCE VOLTAGE (VOLTS)Figure 7. Capacitance Variation
