HOS-050C ,Fast Settling Video Operational AmplifierGENERAL DESCRIPTION
Thc Hos-oso, Hosmm, and HOSVOSOLZ p amp» am: very
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HOS-050-HOS-050C
Fast Settling Video Operational Amplifier
ANALOG
DEVICES
FEATURES
80ns Settling to 0.1%; 200ns to 0.01%
100MHz Gain Bandwidth Product
55MHz 3dB Bandwidth
100mA Output (a t10V
APPLICATIONS
D/A Current Converter
Video Pulse Amplifier
CRT Deflection Amplifier
Wideband Current Booster
GENERAL DESCRIPTION
Thu HOS-OSO, HOS-OSOA, and HOS-OSOC op amps arc very
high speed wideband operational amplifiers dcsigncd to complc-
ment the Analog Devices' lines of high spccd data acquisition
products. They feature a 100MHz gain bandwidth product; slcw
rate of 300Vps; and settling time of 80ns to t 0.1%.
The HOS-050A, HOS-OSO, and HOS-OSOC have typical input
offset voltages of lOmV, 25mV, and 45mV, respectively.
All models have a rated output of t 100mA minimum, and an
exceptional noise spcc of only 7wV rms, dc to ZMIIZ: they are
ideally suited for a broad range of video applications.
FAST-SETTLING OP AMPS
At one time. operational amplifiers could bc spccilicd according
to slew rates, bandwidth, and drive capability; and these param-
eters would be sufficient. Settling lime was not considered until
the use of high speed video DA converters bccamc widespread.
The conversion specd of the irA can be limited by the settling
time of the output amplifier, so it has become essential to select
an up amp whose settling time is compatible with the DA
converter.
The increased emphasis on settling time has, in some cases.
created a preoccupation with slcw rates in the minds of some
designers. But slew rate is only one component in cstablishing
settling limc.
Thc amount of ovcrshoot, and the ringing which are present at
the end of a step function change also have an effect. These
paramctc'rs, in turn, are intlucnccd by the bandwidth tor lack of
it) when opcrating the op amp with closed loop gains greater
than onc.
Information furnished by Analog Devices is believed to be accurate
and reliable. However, no responsibility is assumed by Analog Devices
for its use; nor for any infringements of patents or other rights of third
parties which may result from its use. No license is granted by implica-
non or othemuse under any patent or patent rights of Analog Devices.
COMMON MODE KEJECYION
MN LOOP VOlUGE GAIN
Fast Settling
Video Operational Amplifier
GAIN noon LOAD)
"---'"--'-""--"'.. i
cMn "s t
w \ us
no so 5
, w 100 u lol Inc- "A mu 100M
FREOUENCT - Ml
Figure l. HOS-050 Frequency Response
VOWKR DISSI'A TON
15W MAX "x . TWW
“A - Imw
Um ' SO'CW
AMBIEN'
[sTlkk AM)
WWII DISSI'AHDN
VS YEWKMYURE
FOR VO-l PACKAGE
" so " ‘00 I23 thet
TEMPERATURE _ "C
Figure P. Power Dissipation vs. Temperature
PO. Box 280; Norwood, Massachusetts 02062
Telex: 924491
U.S.A.
Cables: ANALOG NORWOODMASS
SPECIFICATION S (typical @ + 25°C and t 15ll unless otherwise speeified)
IDIIIII.
Model HOS-OSO
ABSOLUTE MAXIMUM RATINGS
Supply Voltages (Vs) , 18V
Power Dissipation See Figure 2
Input Voltage ' Vs
DWerential Input Voltage t Vs
Operating Temperature Range (case) - 55''C to + l25°C
Junction Temperature 175''C
Storage Temperature Range - 65°C to + 15trC
Lad Temperature (soldering, 10 sec.) 300°C
DC ELECTRICAL CHARACTERISTICS
Parameter Conditions Min Typ Max Min
Open LoopGain RL = 100ft l00
Rated Output RL = >100!)
Voltage , 10/8 .
Current
(not short circuit protected) , l00 .
Voltage Rt. = >200!) , lo .
Input Offset Voltage Adjustable to Zero
Initial © + 25°C 25 35
vs. Temperature 50 150
vs. Power Supply Voltage 0.5
Input Bias Current
Initial Cd +25'C l 2
vs. Temperature Doubles
Input Offset Current
Initial Gr + 25°C 2100
Input Impedance Io
3:23:30“ }In parallel with 5p gl'
Input Voltage Range
Common Mode , IO l8 "
Differential 18
Common Mode Rejection 70
Input Noise Rpp = l00(l;RF3 = lkn
dc to 100kHz 5
dc to2MHz 7
AC ELECTRICAL CHARACTERISTICS'
Parameter Conditions Min Typ Max Min
SlewRate A = - RR“: = Rm, = soon;
Load = 100tt 300
Noninverting Slew Rate A = 2;RFF = Rrss = ioo0n;
Load = 100ft 320
Overload Recovery 50% Overdrive 400
Gain Bandwidth Product R,., = ltr, = soon 100
SmallSignal Bandwidth, - 3dB = - l;Rm, = Rm = 500n 45
A---t;RFr--RFB--l000n 35
A = -2;Rm, = Rm = 5001,
Rpa = 1000ft 35
A = -4;RFF = Rm, = 2500;
Rm, = I000ft 30
Output Impedance < l
Nuninverting Bandwidth, -3dB A = Zan: = Rm, = 1000tP,
1000 load; 10pFcapacitance
S-volt p-p output 25
4-volt p-p output 30
bvoit p-p output 55
A = 3;RFY = 500ft;
Rm, = I000n;100n,1000iP,
or 2000n load; lOpF
capacitance
10-voll p-p output 17
S-volx p-p output 25
HOS-OSOC
- 25''C to + 85''C
Max Units
200 WV/OC
wV rms
pV rms
Max Units
AC ELECTRICAL CHARACTERISTICS' (Continued) HOS-OSO HOSOSOA HOS-OSOC
Parameter Conditions Min Typ Max Min Typ Max Min Typ Max Units
Noninverting Bandwidth, - MB A = 5; Rm, = soon;
(continued) Rm, = 20000; 1000, 1000n,
or 200011lozd/ l0pF
capacitance
S-volx p-p output 15 . . MHz
4-vtylt p-p output 30 . . M Hz
Z-voll p-p output 40 . . M Hr.
l-voll p-p output 40 . * M Hz
FuilPower Bandwidth Output = + IOV/ -8VCa t lOOmA;
5% distortion 5 . I MHz
SettlingTimeto0.1% A = - l;Rn.- = Rm = 500n
inverting err = ' w
(See Figure S) VOL” = :2.5V
Noninverting A = 2; Rn: = Rm = 5009
Max Load capacitance = 7SpF
Votrr = , w 200 . . ns
VOU'r = t2.5V 135 . I ns
Harmonic Distortion = - P, Load = 10009
(See Figure 9) Signal = 4MHz; 2V output - 63 . . dB
Noninverting Harmonic A = 2;Rpp = Rm, = 1000n;
Distortion (See Figure 10) Load = 10000;
Signal = 4MHz;2V output - S9 . . dB
Power Supply
Voltage Rated performance t IS . . V dc
Voltage Operating range t 12 I8 . . . . V dc
Current Quiescent ut 20 25 . . . . mA
Power Consumption Quiescent 0.6 . . W
Power Dissipation 1.25 . . W
Temperature Range
Operating (Case) (See Figure 2 for - 55 + 125 . - 25 + 85 "C
Storage Dcrating Information) - 65 + 150 . . ' I "C
Meantime Between Failurcs MlL-HNBK 2I7; Ground; 2.78 . ' Hours
(MTBF) Fixed; Case = 70°C A ttts
883B Processing
Notes:
'Sperirscation for lnmng Mode unless othetwise noted. lndmdunl socket "setttbliestone per pmnrc available from AMP " pan number 63308084).
"tem'rscatsott "me u HOS-OSO Speciricaaons subtect lo change without nouce.
OUTLINE DIMENSIONS H0S-050/A/C
Dimensions shown in inches and (mm).
F-oss '")--1
0.025 i
(0.64) 0.165
(9.5) LONG, MIN 0.018
(0.46) DIA
CAN -l l’tis)
PINS ARE GOLD PLATED
BOTTOM VIEW
PIN DESIGNATIONS
PINS FUNCTION
GROUND
OFFSET ADJ'
OFFSEYADJ'
- INPUT
' INPUT
UONOUILUNd
" OUTPUT
'PINS FOR CONNECTING OP‘HONAL
OFFSET POTENTIOMETER.
OUTLINE AND PIN DESIGNATIONS
GROUND
OFFSET
ADJUST'
V . 'PINS FOR CONNECTING
OPTIONAL OFFSEY
pt2TENT1t2METER
T0-8 PACKAGE
BOTTOM VIEW
OFFSET
ADJUST' GROUND
The HOS-OSO Series stands up under close scrutiny of these
characteristics because of its 100MHz gain bandwidth product.
The use of these amplifiers in a wide variety of applications has
confirmed their suitability for video circuits.
The HOS-OSO is also available with MlL-883 processing. Model
numbers change from HOS-050 t0 HOS-OSOB: and HOS-OSOA
t0 HOS-OSOAB.
VOLTAGE AMPLIFIERS/CURRENT BOOSTERS
Video op amps such as the HOS-050 are generally characterized
by high gain bandwidth products, fast settling times. and high
output drive.
One of the most common uses of video op amps is for D A
converter output voltage amplification or current boosting.
Figure 3 is one example of this type of application. In this circuit,
thc intcrnal rcsislancc of thc DA is the fccd forward resistor for
the op amp.
t‘n. . ISV
544 743%,; ...
los'' . . vot uct
OU'PU'
omnut coNVOqtrF1 BIPOLARd‘
vNPIllS nus" ' "05.050
IUNIPOLAI m. lnilmA>
IBIPOlAR m. 511mm
Figure 3. Inverting Unipolar or Bipolar Voltage Output
The HDS Series Dr'A converters are fast-settling, current output
D/As available in 8-, 10-, and 12-bit resolutions. Both TTL and
ECL versions are available, and settling times range from lOns
for 8-bit units through 40ns for 12-bit units.
The circuit which is shown will provide a negative unipolar
output with binary coding on the input, and bipolar offset ground-
ed. It will provide a bipolar output with complementary offset
binary coding on the input, and bipolar offset connected to lo.
An approximation of the total settling time for the DA op amp
combination is calculated by:
Ts = \ T1r'+ To"
where To is DA settling time and To is HOS-OSO settling time.
This approximation is valid because both the WA and the HOS-
050 exhibit 6dB octavc roll-off charatcristics (single pole response);
and the combination of low D/A output capacitance and op amp
input capacitance does not materially affect the formula.
The user of the HOS-OSO should remember the current ilowing
in the feedback resistor (RI) must be subtracted from the output
available from the HOS-050.
There is a tendency, because of this fact, to use a high value of
feedback resistor to assure maximum current drive being available
for driving low impedances; but this approach may create undc-
sirable side effects.
Calculating the minimum load that can be driven under two
conditions of feedback resistor values will serve to illustrate the
difference.
Assume the feedback resistor value is 500it. If output voltage of
the HOS-OSO is ID volts, and output current is l00mA, minimum
load would bc:
Eo max 10V lOV
lOOmA 20mA 80mA
125tt minimum load
lo max [Rm
where: En max = peak voltage needed
lo max = maximum continuous current HOS-OSO can
produce
lmn, = current in feedback resistor at peak voltage
Assume the feedback resistor value is 5,000it. Minimum load
would be:
iio max ION' lOV
IR“, lOOmA 2mA 98mA
102tl minimum load
lo max
Designs which strive for driving a minimum load (by increasing
the feedback resistor) can create settling problems because of a
fundamental characteristic ofop amp circuits . . . the higher the
feedback resistance, the slower the system response.
This phenomcnon is the result of increased impedance for driving
stray capacitance in thc circuit employing the op amp, and
fixed capacitance in thc summing node.
Impedance, need to be kept as low as possible consistent with
low distortion: and stray capacitance need to be eliminated t0
the maximum possible extent. A large ground plane structure is
recommended to help assure low ground impedance. In addition,
0.11.117 ceramic capacitors and 3-l0wF tantalum capacitors con-
nccted as close as possible to power supply inputs will decrease
the potential for parasitic oscillations and other noise signals.
Another argument for limiting the size of the feedback resistor
is because of its effect on bandwidth. Bandwidth of the HOS-OSO
op amp and the value of thc feedback resistor are inversely
related.
At any given gain of the op amp, the gain setting with the widcst
bandwidth will be the one which employs the lower value of
lbcdback. As an example, a gain of I can he achieved with RH.-
- Rm - .500iliorRrv - Ri-n - 1,000il. Small-signal/Nath
for the first combination is typically 45MHr.; bandwidth for the
second is typically 35MHz.
OFFSET AND GAIN ADJUSTMENT
Figure 4 shows a method of using the HOS-OSO op amp which
allows adiusting thc offsct and gain of the output voltage.
m F SI r
An.msv
\ o-i')--,
H i. l 3
numuns I mm
lllSUMMlNk; -....--" ADJUS'
Asrussmu \ $3.4".
vs.tF-qnN--4
cam l','y s)
Figure 4. HOS-050 Offsetand Gain Adjust
As shown, thc gain of the circuit is established by the equation:
G = _ -
( Rin..
where Rea, is the total of RGMN and Gain Adjust.
Once the user has established the desired gain for the illustrated
circuit, the value of Ito can be used to determine the correct
value of Rorr:urr with the equation:
R - V(XI " Rin,
t)rT'h'liT' - - T
where .Mio is the desired amount of offset on the output.
